Saturday, 14 March 2015

Radon Measures - Daughters of decay

Greetings!

Occasionally, I abandon scope — and get on my apple box to rant and wave.
So click here if you want something about circuitry.

A dear friend suffers in the terminal stages of lung cancer. She, a non-smoker, can't figure out how this happened. We'll never know, however, might it have been radon gas exposure in the former old basement suit she lived in for decades?

We bought a radon gas meter that runs a photodiode, a microcontroller and some DC circuitry to perform alpha spectrometry and display the data means.


Above — Day 1 of radon gas measures in my basement lab.

I won't write much about radon gas since good links abound Link1  Link2. Canadians measure radon concentration in becquerels per cubic meter (Bq/m³), while in the USA, they express it in picocuries per liter (pCi/L). I hope my  3 -12 month radon measures stays low and look forward to viewing the changes over seasons and after rainstorms. Hopefully I won't have to make home renovations like my friend Greg did. He lives in our general area.

I get 3 IEEE publications. IEEE Spectrum ran a DIY Radon Detector article last year and here's a link although it's sans the code and schematic.

Remember all the noble gasses? The chemistry fascinates me and its worth reading about. For much of us, alpha radiation exposure primarily comes from inhaling radon and its decay products — it's now the leading cause of lung cancer in non-smokers.

Don't assume that because Bob and Sally's house down your street tested OK, that your home is safe. This is another "To Measure Is To Know" test case. It's horses for courses.

Actually, some of us guys get a bit casual about cancer prevention: How many of you still smoke, go out in the sun all day with no UV blockade, ignore our doctor's advice to get a colonoscopy, or to receive the dreaded prostate sweep? Feeling uncomfortable? This all pales in comparison to the suffering of our friend with lung cancer,

Back to my lab with a radon detector gathering data. 
Best!

Saturday, 7 March 2015

Etherkit Si5351A Breakout Board Update

Jason, NT7S recently shipped the Etherkit Si5351A BOB's and I got mine this week.






This BOB made a huge splash and forms a bedrock circuit to anchor future test and measurement products from Jason.

Stay tuned for updates from Etherkit or the NT7S Twitter feed.




Saturday, 21 February 2015

Regenerative Receiver #4

Hi gang!

This Winter, after a ~4 year hiatus from regenerative receivers, I built 4 while studying the plethora of published designs in print and on the web. How do you describe the sounds that regens deliver? Perhaps the adjective "screechy", or adjective-verb phrase "alive with vibe" might do ---  and when tuning across a SWL band they emit those classic wee-woo sounds that signal we're close to receiving some yet unknown, far off, station.

Many regen authors boast "high performance" or, like a Markov chain, their boosted outcome appears dependent on the state of whatever modulation mode your tuning -- or which knob your tweaking at the moment. Few measures are ever shown in the regen literature. Some designers embrace minimalism, while others unleash parts with fits of fury. Compromise, subjectivity, mysticism, sci-fi, nostalgia ---- it's all here. Joy.

As as mere regen receiver student, I'll offer my experiments with my regen #4 in hopes they might prove useful at some level.

My inspiration for this particular receiver comes from the work of simply amazing builder Makota, 7N3WVM. While a minimalist, his designs pitch common sense innovation and deliver maximum spark for us experimenters.

Makota's website:  http://www.qsl.net/7n3wvm/

The base receiver for my design may be seen at  http://www.qsl.net/7n3wvm/regen.html

It features a Colpitt's oscillator AC coupled to the tank for the Q multiplier plus a separate, low current FET detector. Many have copied/adapted his core regen design, including Dan, N1BYT in the WBR. Dan added his balanced LC circuit with ultra super-light coupling.  Dave, AA7EE also applies a SPRAT fueled Makota design in his Sproutie receiver.

Regen #4 schematic Part 1

Regen #4 schematic Part 1

 
Above — The entire regen #4 schematic.

I'll discuss the stages from left to right.

RF Preamplifier

We hear it over and over --- regens leak RF from the tank to the 'tenna. The often used, common base, or common gate RF amplifier serves as my favorite way to boost antenna-to-tank isolation, plus allows the use of crappy antennas when antenna space gets constrained.

The 500 Ω pot also reduces leakage and I normally just open it "a crack" since my antenna is a full sized 1/4 wave vertical on the 40M Ham band and the preamp offers gain.

No question — if you run the RF gain pot too wide open -- on a strong signal, you may cream the otherwise well behaved regen circuitry and make some bad noises.

The worst case antenna port leakage of regen #4: ~-41 dBm.

Above — The worst case antenna port leakage of regen #4: ~-41 dBm.  In this experiment, I turned both the RF gain and the regen pots fully clockwise! The rig was writhing in spasm with such a setting --- normally both are set close to fully counter clockwise.

Typical AM reception antenna port RF leakage.

Above — Typical AM reception antenna port RF leakage.  I listened to some AM stations like Radio Habana and others farther up the 49M band. With typical AM RF gain and regen control settings, the leakage out of the antenna connector was -73 dBm.
So the leakage will fall somewhere between the worst case and typical for AM reception -- I can live with that.

Feel free to drop the preamp current by increasing the 3K3 resistor. When I hear the word preamp, I think "run some current" -- even, still, it's just 2.24 mA.

Regen #4 breadboard

Above — Regen #4 breadboard

Regen #4 breadboard front view.

Above — Regen #4 breadboard front view. I once read you gotta run a chicken-head knob to really wrestle the audio pot into submission on a regen.

Tank and Q Multiplier

I ran a single, grungy, air-variable capacitor for tuning. My receiver tuned 6.69 - 9.2 MHz
but lacked the fine tuning needed for proper SSB and CW work. I suggest that builders apply standard VFO techniques like a few C0G/NP0 fixed capacitors for temperature stability and some way to provide fine tuning such as a small delta C capacitor in parallel with the other tank parts, or perhaps, a gear reduction tuning knob.

I can't stand temperature drift in my receivers, but varactor (or rectifier diode) tuning might work.

The 8:29 turns inductor ratio is ripe for experiments. As you reduce the smaller winding from 8 turns too a lower N, more of the RF amp's signal will shunt to ground via the collector's 0.1 µF bypass capacitor. I also built a version with no RF amp.

I built the Colpitts oscillator first, added the LC tank and then watched the signal amplitude and frequency in my 'scope + frequency counter as I turned the tuning capacitor. The old make a stage ---  then test that stage thang.
Then I built the RF preamp,detector and AF preamp.

A 470K resistor isolates the Colpitt's parts from the front panel 10K DC bias (Colpitt's amplitude) control. The 22K resistor sets the maximum Colpitt's amplitude and the 3K3 R, the minimum. You may have to experiment with the 3K3 resistor to find the resistor value that allows the Colpitts to just barely turn off but not go to 0 VDC.

If you omit this resistor, you'll hear what it does -- as you slowly turn the 10K pot clockwise from fully counter clockwise, a "bump" sounds as the BJT turns on. You apply the nearest standard value resistor that just eliminates that bump; for me it was 3K3 Ω.

I omitted the 10 µF bypass capacitor 'tween the wiper and 470K resistor in my design from Makota's original design since it causes a small response delay when changing the 10K pot.

Detector and AF Preamplifier

I extended Makota's detector by morphing it to a hybrid cascode.The hycas detector hikes reverse isolation plus lifts the output AF voltage and impedance.

1 experiment worth considering: Remove the 6K8 source resistor and solder a really short lead to a 10-25K pot wiper and 1 outside terminal. While listening to some signals, adjust the pot to find the sweet spot yielding the best sensitivity + AF gain. Remove the pot, measure its resistance and replace it with a nearest standard value resistor. After that, you might try the same procedure with the 2K7 collector resistor while listening to some strong signals. That's how I came up with my values as shown in the schematic.

In regen #4, most of the AF voltage gain occurs in the detector plus the following feedback pair.
The shunt feedback pair is a low-level only, cheesy, popcorn preamplifier I often throw in my experimental receivers. While this preamp looks crazy and won't win awards for temperature stability, its harmonic distortion is reasonably low:

An FFT of the regen #4 AF preamplifier @ ~1 KHz.

Above — An FFT of the regen #4 AF preamplifier @ ~1 KHz. The 2nd harmonic lies 52 dB down while all others are > 62 dB down. For low-level applications only. 2.52 mA total current.

You've noticed the 180 pF cap from output to input? Without a 100 - 220 pF cap in parallel with the 100K feedback cap to lower the preamplifier bandwidth, you'll hear audio oscillation.

DC Voltage

I ran my standard, homebrew, well filtered 12.2 volt DC power supply for my regen and heard no hum. Many prefer a battery supply and in that case, its a good idea to add a voltage regulator to keep a steady DC current in the Q multiplier and detector stages as the battery fades. Ensure you decouple and bypass well in any case.

An example ripple filter used to scrub off noise from the DC supply


Above — An example ripple filter used to scrub off noise from the DC supply. I might place this after a voltage regulator going to the Q multiplier and detector. If you use such a filter, a decoupling resistor plus bypass capacitor is still required in every stage of the receiver as shown in the regen #4 schematic.

AF Power Amplifier

In most regens, you'll see a 10 µF or so capacitor between pins 1 and 8 of an LM386 — this cranks up the gain to 200 and with it; noise and distortion.

I'm going to make 2 bold statements: [1] The LM386 in the low gain mode with some minor tweaks makes a very nice audio power amp. [2] It's unlikely you could build an AF power amp with the same clean average power capacity having the same or less distortion.

An LM386N-4 schematic with the needed bypass and feedback tweaks to make it sing sweetly


Above — An LM386N-4 schematic with the needed bypass and feedback tweaks to make it sing sweetly like Montserrat Caballé.  I showed the functional schematic earlier. Most LM386 users stick a capacitor between pins 1 and 8 which bypasses the 1.36K emitter resistor and this application (OK in some situations) resulted in the LM386 getting labels such as "a distortion machine", or a "compromise part". I continue to applaud the team that designed this part.

I've applied the LM386 like this for years, but have never shown any measures. Here we go:
 
An FFT of an LM368N-4 driven with ~ 1KHz sine wave to output 3.06 Vpp into an 8 Ω resistor load.

Above — An FFT of an LM368N-4 driven with ~ 1 KHz sine wave to output 3.06 Vpp into an 8 Ω resistor load. The second harmonic is ~ 64 dB down! At this drive, the power = Vpeak ^2 / 2R -- so (1.53 * 1.53) / 16 = 146 mW.

This is roughly the clean power you'd get from a 2N4401/2N4403 complimentary pair;  however, to get distortion this low would take some serious engineering, parts and measurement for the average Ham experimenter.

I cranked up the drive to output 5.27 Vpp

Above — I cranked up the drive to output 5.27 Vpp: Average power now = (2.635 * 2.635) / 16 = 434 mW. Look, the distortion remains low.

The time domain output with my LM386 driven to the point where I can just detect signs of distortion: 5.71 Vpp or 520 mW.

Above — The time domain output with my LM386 driven to the point where I can just detect signs of distortion: 5.71 Vpp or 520 mW.

 Adding back the FFT shows the harmonics are still down ~ 52 dB  from the fundamental. Still reasonable at over 1/2 W.

Above — Adding back the FFT shows the harmonics are still down ~ 52 dB  from the fundamental. Still reasonable distortion at over 1/2 W power.

Pushing the drive to get obvious clipping of the sine wave results in a 2nd harmonic of -40 dBc.

Above — Pushing the drive to get obvious clipping of the sine wave results in a 2nd harmonic of -40 dBc. That's my threshold of allowable distortion tolerance in a popcorn radio AF PA. P = 599 mW. At normal room volume, you might get this on some stronger signal peaks.

The 4 controls on a regenerative receiver keep your hands busy. Some combination of those 4 tweaks will give you the best sounding audio and hopefully keep the signal level where minimal clipping of peaks occurs.

The LM386 seems OK in my book. If these experiments don't show the benefits of measurement, then I'm afraid nothing will. 

In regen #4, my strategy included building up most of the the AF voltage gain with the hycas detector + a feedback amp using relatively low noise 2N4401 BJTs.  The LM386 adds some gain, but minimal and the result is a popcorn, relatively low noise + distortion AF chain that sounds OK.

No question, some builders can build a better AF mousetrap and I encourage them. However, for a low-fi regen receiver, I posit the LM386 in low gain mode with some tweaks will save a lot of parts plus space and give reasonable AF into a speaker. As ever, you'll decide what works best.

Out Takes

A double-tuned tank featuring varactors as the variable C.


Above —A double-tuned tank featuring varactors as the variable C. At some point, I'll couple it to a Q multiplier and take a look. I built a ton of regen-related circuits in Jan - Feb 2015. Great fun.

A sweep of the above double tuned circuit tuned at 6. 37 MHz.

 Above — A sweep of the above double tuned circuit tuned at 6. 37 MHz. The higher than expected insertion loss arose from the mismatch at the output end ( 29t : 10t ), plus the low Qul of the varactors.

A GPLA generated transfer function

Above — A GPLA generated transfer function. I designed the 49M band double-tuned circuit with the LADPAC software that ships with EMRFD.

Addendum:

A ton of people view this blog by clicking on links from Twitter. I joined up -- see My Links

Thank you

Todd, -VE7BPO-

Thursday, 12 February 2015

The 5 Watter and All That

When I think of Michigan, in my mind's eye, I see Doug DeMaw, QRP rigs galore, chef Mario Batali and the Michigan Wolverines NCAA football team from Ann Arbour. From now on, I'll also include Michigan QRP Club's print journal -- The 5 Watter -- T5W for short.

No 1 really kept track how long its been published, but Mikey, WB8ICN, began saving back issues of the T5W quarterly in the early 90's.

That's impressive. Small-scale journals peak my interest since they capture local flavor, unite members and kindle creativity. And, they've kept it in print just like day 1. Do you find there's something inspiriting about holding a paper book or periodical now and then?

I'm helping Mikey with some of the technical content and really enjoy contributing something along with the vibrant bunch who publish T5W. Keep up the good work crew!




Above — Mikey took some photos for me. Some sort of T5W archive seems prudent.
Michigan QRP Club link

Omega

When reading technical material, do you see the ω character? For example:  XC = 1 / ω*C  ….   so C = 1 / ω * XC etc. For some reason, I slept through the lecture and did not know what to call ω all these years. In 2015, I awakened --- it's the symbol for lower case omega. We use her upper case sister all the time: .

Commonly you'll see ω = 2 pi  * F . Engineers refer to ω as "omega" or the "angular frequency."

What are you working on?

I love to hear what you're up to. It seems that Arduino projects top the list. Making DDS clocks has ranked high for years --- now the Si5351A stirs the mix. I can't wait 'till mine comes from Etherkit. I've never applied Arduino -- but we've made very cool, original stuff with Netduino including robotic LED-laden cat toys with multiple sensors to keep the cats occupied. class cat_toy { };

I designed/built 3.7 regen receivers this Winter (1 isn't quite finished). I may present my #4 design if it works OK. It's almost ready for power up and testing. I still remember making my first regen at around age 10. This guy: Link.  I never got it to work.

I'm not a big fan of regenerative receiver audio (it hurts my ears) but still revel in their simplicity and versatility.
After that, I'm making my first receiver for listening to Jupiter -- venturing into amateur radio astronomy.

Happy building!

Saturday, 7 February 2015

Trixie 2 --- low current, junkbox, 40M Band DC receiver

Greetings!

In 2011, I made a 1 transistor regenerative receiver that I called the Stupid Simple. I ran a single BJT ---  with just enough bias to barely turn it on. To date, I've never built or measured a regenerative detector with higher AF output voltage.

Remembering the sublime sensitivity of this little bipolar gem, I set out to make a DC receiver for the CW + SSB 40M band with only discrete, junk box parts --- plus running as little current as possible.

I may write up a formal blog post with some measures when I make a presentable version of Trixie 2  ---- but until then, here's the raw bench version -- something I've never shown before.

Despite its simplicity, I spent many hours trying to make this radio sound decent. You can't make a silk purse from a sow's ear, but I really love this little receiver and enjoy its performance versus detector current (and cost) factor.

Trixie 2 front-end end AF preamp schematic.

Above — Trixie 2 front-end end AF preamp schematic. The entire stage current draw = 2.54 mA. A 1K2:8 Ω or 1K:8 Ω AF transformer with 0.22 µF HF bypass on the high impedance side provides the only serious low-pass filtering of the output AF. The 0.22 µF caps may be decreased to as low as 0.1µF to preserve sibiliance -- but this also boosts noise.

The 39 pF cap matches the transformer to a nominal 50 Ω antenna input. You may wish to replace the 47 pF cap with a trimmer, however, it tunes the bottom 200 KHz of the 40M band OK.

I ran an available LO power of 7 dBm from my homebrew signal generator. In the old site archive it's shown on a page called VFO 2011.

The optimal LO drive is best determined by the builder. 5 - 7 dBm works OK and you may wish to experiment to find the best LO drive in your need to balance mixer harmonic cancellation, versus sensitivity, versus suppressing AM detection.

If you match 2 transistors for DC beta at a similar collector current you can omit the 1K balance control, however, why bother?

You'll hear the delicious din and chatter of multiple AF products from both sidebands. Normally, we low-pass filter the AF channel -- or perhaps cancel the opposite sideband with phase shift circuitry ; but not in Trixie 2.

2N3904s cost pennies a piece -- I felt tempted to use my favorite leaded BJT series, the 2N4401/03, however, here, we're digging deep in the junk box.


I actually enjoy the visceral sound of raw product detector AF output since it makes me think about mixer function and how to best design and tweak AF circuits in more robust receiver designs such as the R2 by Rick, KK7B.

Trixie 2 seems a perfect consideration for a low current, battery power, bare bones receiver.

I've detected 0 hum and no local broadcast band AM radio. Despite the balance control and transformers, Trixie 2 will tune in and detect AM SWL stations, however, for the most part, they lie way in the background and even a strong carrier disappears 3-4 Hz away from center frequency.

Above — Trixie 2 AF power amp.


Above — Trixie 2 AF power amp. The key to solid, linear AF voltage amp design = feedback. Anyone can run some voltage amps together to build up the AF signal --- but doing this with low distortion takes finesse and measurement -- I hope to get better at it over time.

Only 1 voltage amp is required in the Trixie 2 PA. To keep the quiescent current down, I ran 3 power followers in parallel to obtain a clean maximum average power of 335 mW. This keeps the audio signal clean on peaks when listening at reasonable loudness. With parallel followers, you only need 2 diode drops to forward bias them into A/B and this keeps the quiescent current down.

I also made a headphone version of this amp --- you can only run 1 or 2 pairs of followers and further can raise the 470 Ω resistors on the emitter follower to drop quiescent current.

In a battery powered version, I might apply another 1K:8 Ω collector transformer and run a single transistor amplifier for the AF PA.

FFT of the AF power stage at ~~1/2 maximum average power

Above —FFT of the AF power stage at ~~1/2 maximum average power. The second harmonic is 43 dB down. Not great, but good enough for a bare bones receiver like Trixie 2. You can boost the distortion performance by running more feedback and increasing the current through the emitter follower. For example, drop the 470R resistors to 330 or 220 Ω.

Video 

Below — 1 good way to real-world test a receiver is to tune in an around a CW pile up. This often represents the worse case for a receiver since some of the guys are likely to run power.  A DPDT switch with an in or out 14 dB attenuator pad on the antenna input proves invaluable to low IMD product detectors.

My video gear, lighting and technique sucks and my camera microphone circuit is clipping some of the peaks!  Warts and all..







Trixie 1

Above —The Trixie 1 --- my prototype that offered strong sensitivity but suffered from terrible in-band AM detection. This low current detector works well for novelty-grade SSB, CW and AM detection (it also works FB as a modulator) Balancing the product detector transformed this simple product detector into something useful (Trixie 2), however, I may use this unbalanced detector in my next, simple AM SWL radio.



Above —The prototype of my AF power stage.  In 1995, Wes taught me to always take a circuit that you know works OK and then alter it. That's what I did when designing the AF power amp --- wise words.

Conclusion

Simple circuit design yields great fun and less-than-usual parts wastage during prototyping. I plan to evolve Trixie 2 into something for the trail.

73!

Friday, 6 February 2015

NT7S --- Si5351A Breakout Board ---- Final Stretch ----

Ask all strata and sects of builders which Hams energize our hobby and you’re sure to hear Jason, NT7S mentioned. Thorough, passionate and humble, Jason’s well on track --- exceeding all expectations with his recent, high-octane, Si5351A crowdfunding blitz. With only a few days left, please consider jumping in to support Jason’s effort to launch his breakout board plus seed future projects.


NT7S Si5351A BOB Crowdfunding Link


Saturday, 24 January 2015

Crystal Parameters --- Experiments with a Tracking Generator + Spectrum Analyzer

Greetings!

I love finding ways to measure parts and circuits with my tracking generator + spectrum analyzer (TG + SA).

I show early experiments with a jig developed to derive crystal motional parameters with a TG +SA plying the G3UUR method. Crystal parallel capacitance (C0) is measured separately with an LC meter. My hope is to accurately characterize fundamental crystals in the 20-50 MHz range to make crystal ladder filters for VHF projects.

Schematic of the series jig for characterizing xtals with the G3UUR method.

Above — Schematic of the series jig for characterizing xtals with the G3UUR method. Each 50 Ω port gets an impedance drop by a trifilar transformer and L-pad down to 1.811 Ω to help eliminate any xtal parallel capacitance effects during measurement. The L-pad attenuates the signal by ~ 10.1 dB to help establish the crystal input/output Z.

Cs, the series capacitor = a Vishay 1%, Q = 2500 MHz @ 1 MHz, size 0805 C0G capacitor measured at 30.8 pF before going into the circuit. The transformers = 8 trifilar windings on a FT37-43 ferrite toroid.

1 view of the early breadboard with a 40 MHz xtal in the holder

1 view of the early breadboard with a 40 MHz xtal in the holder

Above — 2 views of the early breadboard with a 40 MHz crystal in the holder. I shortened and better grounded the 9:1 Z transformers after taking these pictures. Built on double-side Cu board, several Cu via wires pass through to establish a solid ground plane. This helped boost the input + output return loss to get close as possible to the desired crystal 1.811 Ω source and load Z.

The switch  = a slide-on shorting switch often employed in computer motherboards.

Measures with a 40 MHz Crystal

A sweep of the crystal series resonant frequency.

Above — A sweep of the crystal series resonant frequency. I ran the RBW at 100 or 30 Hz but either worked fine — and of course, 100 Hz gives faster sweeps. The series resonant frequency = 40.002098 MHz.

A sweep with the switch shorting pin is added

Above — A sweep after adding the Cs switch shorting pin with a gloved hand and allowing time to stabilize before recording frequency and power. F = 39.990770 MHz. Power (referenced to 0 dBm) = -33.24 dBm.

A sweep with the shorting pin still on the switch --- but the crystal removed and replaced with a copper shorting wire stuck into the crystal holder.

Above — A sweep with the shorting pin still on the switch --- but the crystal removed and replaced with a copper shorting wire stuck into the crystal holder. Through power = -28.39 dBm.

Delta  P = the power difference in dB between the series resonant crystal measure and the power recorded with the crystal holder shorted by a Cu wire [both with the 30.8 pF capacitor shorted]. Delta P = 7.13 dB.

Crystal C0 = 2.73 pF as measured with an AADE meter.

Calculations:

 Professor Natasha shows Cm and Lm calculations.


Above — Cm is calculated with the standard formula. After --- calculate the capacitive reactance of Cm and insert this X into the formula to calculate Lm. A scientific calculator makes these equations easy to crunch. Typically we would express Cm as 1.99E-14 on a calculator.

At this point, we've calculated crystal Cm, Lm and have enough data to calculate the ESR at the series resonant frequency + the unloaded Q.


I asked Victor 4Z4ME for help with the calculations for ESR, since once you know the crystal series resistance, Qul may be calculated. Victor sent the below figure that shows how to derive the equation to crunch ESR. Note: 1.8 Ω was used instead of 1.811 for clarity.


In order to calculate ESR and unloaded Q, we first calculate the ratio of voltages V1/V2 from the base equation V1/V2 = 10^((P1-P2)/20 . Exquisite math yields Rx (ESR).



Equations to calculate the ESR and Qul.   Professor Natasha.



Above —Equations to calculate the ESR and Qul. The ESR formula that Victor showed earlier is further simplified to the right of the green arrow [ESR = 3.622 * (V1/V2 - 1) ]. We then use ESR to calculate the unloaded xtal Q as shown.

This 40 MHz job @ 43.4K = a low Q crystal, but it might work OK in a wide IF filter that follows a VHF receiver's first mixer. Most of the crystals >= 30 MHz fundamental I've tested have a Qu < 100K.

Building a collection of fundamental crystal >= 20 MHz proves difficult for me. Several eBay crystal offerings touted to operate on the crystal's fundamental frequency turned out to be overtone crystals. Crystal purchased from vendors like Mouser-Key have better obeyed the their datasheet specification, although, there too, I've found exceptions.

I fundamental frequency test these crystals in an oscillator that outputs to my 50 Ω terminated 'scope.

An oscillator I use to test fundamental crystals >= 20 MHz.
Above — An oscillator I use to test fundamental crystals >= 20 MHz. Although, the BJT listed is a MPSH10, a 2N3904 works OK.

The 40 MHz crystal shown in the earlier Cm, Lm, ESR, and Qul calculations vibrating in my crystal test oscillator.

Above — The 40 MHz crystal used for the earlier Cm, Lm, ESR, and Qul calculations vibrating in my crystal test oscillator.

A 30 MHz fundamental crystal in the test oscillator.

Above — A 30 MHz fundamental crystal in the test oscillator.

1 of the many 50 MHz "fundamental" crystals that turned out to be an overtone job.

Above — 1 of the many 50 MHz "fundamental" crystals that turned out to be an overtone job.

Conclusion

I measured a 12.0 MHz crystal with the classic G3UUR crystal oscillator method and compared it to the series jig result. The classic xtal oscillator gave an Lm = of 0.0052 H, while the TG + SA series jig gave an Lm of 0.0041 H.

I'm not sure which 1 is correct? Likely the proof of the pudding lies in the transfer functions of the crystal filters I build informed by this new crystal parameter tool.

While it's no panacea, I enjoyed these experiments and learned a lot. For example, I now have 3 methods to measure crystal Q and feel I've advanced a little in my TG + SA skill set
.
My sincere thanks to Wes, W7ZOI for getting me started on this project and also for a few breadboard parts — plus — big thanks to Victor, 4Z4ME for his equations and support.

Best!